Implementation method for pre-distortion of non-linear devices

ABSTRACT

The present invention proposes a new specific method to calculate and optimise a pre-distorter avoiding the need of time-alignment between input and output of the amplifier. That is, the analogue output spectrum is used directly to compute an optimum pre-distorter, either in digital or analogue format. The solution proposed uses the output spectrum directly to optimise intermodulation performance, rather than trying to match the input spectrum to the output spectrum. That is, the output spectrum (except for a possible gain constant) can be used as input to the optimisation procedure directly. Since the intermodulation products usually are of much lower amplitude than the carriers themselves, it can be taken as the input spectrum without major loss of confinement. The present disclosure outlines in detail the mathematical procedure to actually calculate a proper predistorter using only the ouptut signal.

TECHNICAL FIELD

The present invention relates to optimisation of pre-distortion as a means to linearize inherently non-linear devices.

BACKGROUND

Linearization of inherently non-linear devices is necessary if distortion of signals through the device is to be minimised. Specifically when it concerns amplifiers in wireless communications it is in most cases necessary to limit spurious signal generation at out-of-band frequencies and also in some cases at in-band frequencies. One of the most frequently used techniques involves subtracting the unwanted signal portion from the output of the device by a feed-forward technique. The non-distorted input signal is then subtracted from an attenuated copy of the distorted output signal to give an estimate of the added spurious signal components, which may be again subtracted from the output signal by proper amplification and phase alignment. This technique is as suggested by the description above referred to as “Feed Forward” techniques, FF.

Another method to compensate for unwanted signal components is to find a mathematical operator, which, if applied to the input signal, gives enough anti-distortion to compensate for the non-linearities of the device itself. This operator will if placed in a cascade configuration cancel out the unwanted signal components at the non-linear device output. This technique is referred to as “Pre-Distortion” techniques, PD.

A specific application of non-linear pre-distortion is to combat non-linear effects in power amplifiers for cellular communications. As capacity will drive the evolution of existing and forthcoming standards to deliver a higher number of user channels per bandwidth, amplifiers will have to be used in a broadband fashion. That is, if fed through a non-linear amplifier, these channels or frequencies would interfere with each other and also produce unwanted spurious signals in other frequency bands, which are used by other network providers or mobile users.

A realisation that uses the previously mentioned FF technique is the Multi Carrier Power Amplifier (MCPA). This device incorporates delicate tuning circuits for amplitude and phase matching so that at the end only the distortion part is subtracted from the output signal. A way to strengthen the linearization would be to cascade a pre-distorter or alternatively linearize the internal amplifier itself. In the process of doing so, it is expected that the overall efficiency will also become higher. Another way is to actually take away the FF circuitry and solely rely on a good pre-distorter and good internal amplifier. It is believed that this would beneficially decrease manufacturing cost and also provide a simpler overall design.

STATE-OF-THE-ART

State-of-the-art of pre-distortion is to compare samples of the signals measured at the input and output ports of a non-linear device, and then compensate by amplifying or attenuating the specific amplitude level. In this way a non-linear amplitude characteristic function is obtained by which non-linear effects may be compensated for. Phase adjustment can be made in a similar way.

Another method may incorporate a more detailed algorithm whereby the characteristics of the non-linear device is tracked by time-dynamical methods such as expansion of the Volterra series, in order to find a closed expression for the device. The next step would then be to find an inverse to this function by the same expansion and apply it as a pre-distorter.

SUMMARY

The disclosure of the present invention proposes a new specific method to calculate and optimise the pre-distorter avoiding the need of time-alignment between input and output of the MCPA. That is, the analogue output spectrum is used directly to compute an optimum pre-distorter, either in digital or analogue format.

The method of computing the parameters of the pre-distorter is usually to compare the input signal to the output signal, and then in some manner adjust the parameters in such a way as to minimise distortion at the output of the non-linear device. Usually this means a careful time or phase alignment of input-to-output signals, which makes it a somewhat difficult task to actually implement.

Moreover, it usually involves some sort of modelling of the pre-distorter in conjunction with the power amplifier itself In this way, the optimisation procedure is somewhat twofold in that it needs modelling of two items within the iteration procedure. It would be expected that the iteration process gets rather involved and also takes time to perform.

In the output only method, it poses some problems as how to express the target signal and the actual mathematical equations to solve.

The solution proposed to the above problem is using the output spectrum directly to optimise intermodulation performance, rather than trying to match the input spectrum to the output spectrum. That is, the output spectrum (except for a possible gain constant) can be used as input to the optimisation procedure directly. Since the intermodulation products usually are of much lower amplitude than the carriers themselves, it can be taken as the input spectrum without major loss of confinement. The present disclosure outlines in detail the mathematical procedure to actually calculate a proper pre-distorter using only the output signal.

As a second improvement, the spurious frequency components are directly suppressed to zero, without the need for approximating the target input signal by even a filtered version of the output signal. In this case, only information about a gain constant and at which frequency components or frequency band the pre-distortion should achieve zero magnitude.

A method of optimising pre-distortion means is set forth by the independent claims 1 and 4, and further embodiments of the method is set forth by the dependent claims 2 to 3 and 5, respectively.

SHORT DESCRIPTION OF THE DRAWINGS

The invention, together with further objects and advantages thereof, may best be understood by making reference to the following description taken together with the accompanying drawings, in which:

FIG. 1 illustrates an amplifier with an amplitude gain G, and being described by a non-linear operator H₀(x), the gain G being defined by the relation of average power ratio of x and y;

FIG. 2 illustrates a pre-distorter in a cascade configuration with a non-linear device, whereby the pre-distorter acts as an inverter to operator H₀(x) except for the transfer gain (G) through the device;

FIG. 3 illustrates a first inversion method, wherein the output signal is inverted back to the input signal by using a filtered version of the output signal as an approximation of the original input signal, whereby the inverter also tries to keep the in-band frequency components of the spurious spectrum intact;

FIG. 4 illustrates optimising of a pre-distorter by using only output signal, whereby the pre-distorter is optimised to produce no spurious frequency components in frequency regions A+C only, and the result is that no spurious frequency components at in-band frequency spectrum are forced to be maintained thereby producing an even “cleaner” spectrum than in FIG. 3; and

FIG. 5 illustrates the main steps of the method according to the present invention.

TECHNICAL DESCRIPTION

Least Mean Squares Approach

It is tempting to insert a general pre-distorter at the input of a non-linear device, and then try to optimise the parameters in such a way that a given cost-function at the output of that device is minimised. However, it will prove that such an attempt will cause the optimisation algorithm to find itself in local minima. In general, it is difficult to find a good solution to the optimisation problem in this way. Another way is to invert the output signal such as to equal the input signal. This inverter can then directly be inserted acting as the pre-distorter. As stated above and will be described further below, it is also possible to use only the output signal itself for the calculations with only some minor knowledge of the input signal.

In view of FIG. 1 the following equation may be written down, together with the inverse solution to the equation: H ₀ [x]=yx=H ₀ ⁻¹ [y]  (1)

Likewise, we may write for the signal equality in FIG. 2 that: H ₀ [PD(x)]=G·x or PD(x)=H ₀ ⁻¹ [G·x]  (2)

So, given the inverse operator of the non-linear device immediately gives the pre-distorter function in a straightforward mathematical way. That is, given that the inverse operator actually exists this strictly holds. This suggests that the key issue is to solve Equation (1) above, and then just apply this non-linear operator in cascade with the non-linear device by compensating for the amplitude gain (G).

A somewhat simpler way to solve Equation (1) above, than first estimate H₀ and then try to invert the operator, is to immediately solve for the inverse operator without bothering to solve for the forward case first. That is, part of this disclosure is to solve for the following equation: H ₀ ⁻¹ [y]=x or F[y]=x  (3)

The next step in the proposed method is to expand this operator in, for example, a dynamic Volterra series. Note that also possibly other expansions may be successful. It can be shown [1] that if a system can be described in terms of a Volterra series and if the inverse operator exists, then there must also exist a complete Volterra series that equates to the inverse operator. Already here we recognise that this Volterra series can then be directly applied to the input signal, which will give the necessary pre-distortion to give a linear input/output relation.

Note that we are still discussing input-to-output relations at this stage. In a few steps of the development of this disclosure we will drop this distinction as to emerge at a desired method for output signal optimisation only.

Proceeding with the development of the pre-distorter we may conclude that for example a Volterra series expansion of the following form satisfies Equation (3) above: $\begin{matrix} {{{\sum\limits_{n}{a_{n}y_{k - n}}} + {\sum\limits_{n}{\sum\limits_{m}{a_{n,m}y_{k - n}y_{k - m}}}} + {\sum\limits_{n}{\sum\limits_{m}{\sum\limits_{p}{a_{n,m,p}y_{k - n}y_{{k - m}\quad}y_{k - p}\quad\ldots}}}}} = x_{k}} & (4) \end{matrix}$ for each time sample ‘k’.

It should be mentioned that the Volterra series might not be the only possible description of the pre-distorter. To a designer skilled in the art it is obvious that also other functions or linear combinations of functions are possible. Specifically, the solution to the above Equation (4) may be obtained in a number of ways. In this disclosure we will be using the Least Mean Squares solution (LMS), but also other methods are possible. Further, using notations for Basis functions instead of the individual Volterra terms, we get the following equation in matrix form: $\begin{matrix} {{\left\lbrack {B_{k,1}\quad B_{k,2}\quad B_{k,3}\quad B_{k,4}\quad\ldots} \right\rbrack \cdot \begin{bmatrix} b_{1} \\ b_{2} \\ b_{3} \\ \vdots \end{bmatrix}} = x_{k}} & (5) \end{matrix}$

For instance in the above equation, B=y_(k-n)y_(k-m)y_(k-p) and the b's correspond a's in Equation (4) above. It is also clear from Equation (5) that B can be any basis functions, which when linearly combined approximates the characteristics of the pre-distorter. If, for each instance of time sample k, new values for the Basis functions B_(k) and for the x_(k) values is computed and measured, respectively, we get: $\begin{matrix} {{\begin{bmatrix} B_{1,1} & B_{1,2} & B_{1,3} & \cdots \\ B_{2,1} & B_{2,2} & B_{2,3} & \cdots \\ B_{3,1} & B_{3,2} & B_{3,3} & \cdots \\ B_{4,1} & B_{4,2} & B_{4,3} & \cdots \\ B_{5,1} & B_{5,2} & B_{5,3} & \cdots \\ \vdots & \vdots & \vdots & \quad \end{bmatrix} \cdot \begin{bmatrix} b_{1} \\ b_{2} \\ b_{3} \\ \vdots \end{bmatrix}} = \begin{bmatrix} x_{1} \\ x_{2} \\ x_{3} \\ \vdots \end{bmatrix}} & (6) \end{matrix}$

The above matrix equation is over-determined, which means that the solution cannot be obtained from just inverting the matrix, since only quadratic matrices may be inverted. A solution to this is to apply the LMS solution, which is well understood and has been used in numerous other applications. The steps are as outlined below: B·b=x  (7)

Multiply by B^(H) (complex transpose) from the left: B ^(H) ·B·b=B ^(H) ·x  (8) which gives the following solution: a=[B ^(H) ·B] ⁻¹ ·B ^(H) ·x  (9)

Given the coefficients b of Equation (9) and inserted into Equation (4) constitutes the full pre-distorter for the non-linear device. This is a solution found by only linear methods to an inherently non-linear problem. Below is given specific methods of how to use only the output signal which can be used to further enhance performance in terms of suppressing spurious frequencies while having the in-band signal unchanged. It should further be noted that Equation (9) incorporates both the input and output signals.

Frequency Version of LMS Approach

A frequency version of this method (as described above) may also be employed. Having in mind that each column of Equation (6) constitutes a time sweep for a particular Basis function (Volterra term), we may perform a Fourier transform on each of these columns separately, and also perform a Fourier transform of the right-hand side column. Now we have a frequency version of Equation (6), which may be solved by the same LMS procedure as outlined above. The result should be congruent with the solution shown in Equation (9), which expresses this equation in time domain.

The procedure of the Fourier transform method is outlined as follows. Assume the same equation as in Equation (6) above. In a more clear way to write this equation, we may write it as a function of time as: $\begin{matrix} {{\begin{bmatrix} {B_{1,1}\left( t_{1} \right)} & {B_{1,2}\left( t_{1} \right)} & {B_{1,3}\left( t_{1} \right)} & \cdots \\ {B_{2,1}\left( t_{2} \right)} & {B_{2,2}\left( t_{2} \right)} & {B_{2,3}\left( t_{2} \right)} & \cdots \\ {B_{3,1}\left( t_{3} \right)} & {B_{3,2}\left( t_{3} \right)} & {B_{3,3}\left( t_{3} \right)} & \cdots \\ {B_{4,1}\left( t_{4} \right)} & {B_{4,2}\left( t_{24} \right)} & {B_{4,3}\left( t_{24} \right)} & \cdots \\ {B_{5,1}\left( t_{5} \right)} & {B_{5,2}\left( t_{5} \right)} & {B_{5,3}\left( t_{5} \right)} & \cdots \\ \vdots & \vdots & \vdots & \quad \end{bmatrix} \cdot \begin{bmatrix} b_{1} \\ b_{2} \\ b_{3} \\ \vdots \end{bmatrix}} = {\begin{bmatrix} {x_{1}\left( t_{1} \right)} \\ {x_{2}\left( t_{2} \right)} \\ {x_{3}\left( t_{3} \right)} \\ \vdots \end{bmatrix}\quad\begin{matrix}  \downarrow \\ {time} \\  \downarrow  \end{matrix}}} & (10) \end{matrix}$

Now, taking the Fourier transform of each column in Equation (10) gives the following equation: $\begin{matrix} \begin{matrix} {\underset{\quad \downarrow}{\quad{F\quad F\quad T}}} \\ {{\begin{bmatrix} {B\quad{F_{1,1}\left( \omega_{1} \right)}} & {B\quad{F_{1,2}\left( \omega_{1} \right)}} & {B\quad{F_{1,3}\left( \omega_{1} \right)}} & \cdots \\ {B\quad{F_{2,1}\left( \omega_{2} \right)}} & {B\quad{F_{2,2}\left( \omega_{2} \right)}} & {B\quad{F_{2,3}\left( \omega_{2} \right)}} & \cdots \\ {B\quad{F_{3,1}\left( \omega_{3} \right)}} & {B\quad{F_{3,2}\left( \omega_{3} \right)}} & {B\quad{F_{3,3}\left( \omega_{3} \right)}} & \cdots \\ {B\quad{F_{4,1}\left( \omega_{4} \right)}} & {B\quad{F_{4,2}\left( \omega_{4} \right)}} & {B\quad{F_{4,3}\left( \omega_{4} \right)}} & \cdots \\ {B\quad{F_{5,1}\left( \omega_{5} \right)}} & {B\quad{F_{5,2}\left( \omega_{5} \right)}} & {B\quad{F_{5,3}\left( \omega_{5} \right)}} & \cdots \\ \vdots & \vdots & \vdots & \quad \end{bmatrix} \cdot \begin{bmatrix} b_{1} \\ b_{2} \\ b_{3} \\ \vdots \end{bmatrix}} = {\begin{bmatrix} {x\quad{F_{1}\left( \omega_{1} \right)}} \\ {x\quad{F_{2}\left( \omega_{2} \right)}} \\ {x\quad{F_{3}\left( \omega_{3} \right)}} \\ \vdots \end{bmatrix}\quad\begin{matrix}  \downarrow \\ {frequency} \\  \downarrow  \end{matrix}}} \end{matrix} & (11) \end{matrix}$

Or in compact form: BF·a=xF  (12)

Equation (11) is a frequency version of the original Equation (6). In a likewise manner to the solution shown in Equation (9), we may directly write down the LMS solution to the frequency version as outlined in Equation (11) above: a=[BF ^(H) ·BF] ⁻¹ ·BF ^(H) ·xF  (13) Frequency Weighting

A further improvement to the solution would be to multiply certain rows of Equation (10) corresponding to a certain frequency as to obtain a weighting of these certain frequency responses. Spurious frequency components in certain frequency bands may be given higher importance than other frequency bands. This procedure will improve the solution to give a better pre-distortion performance. $\begin{matrix} {{\begin{bmatrix} {B\quad{F_{1,1}\left( \omega_{1} \right)}} & {B\quad{F_{1,2}\left( \omega_{1} \right)}} & {B\quad{F_{1,3}\left( \omega_{1} \right)}} & \cdots \\ {{C_{1} \cdot B}\quad{F_{2,1}\left( \omega_{2} \right)}} & {{C_{1} \cdot B}\quad{F_{2,2}\left( \omega_{2} \right)}} & {{C_{1} \cdot B}\quad{F_{2,3}\left( \omega_{2} \right)}} & \cdots \\ {{C_{2} \cdot B}\quad{F_{3,1}\left( \omega_{3} \right)}} & {{C_{2} \cdot B}\quad{F_{3,2}\left( \omega_{3} \right)}} & {{C_{2} \cdot B}\quad{F_{3,3}\left( \omega_{3} \right)}} & \cdots \\ {B\quad{F_{4,1}\left( \omega_{4} \right)}} & {B\quad{F_{4,2}\left( \omega_{4} \right)}} & {B\quad{F_{4,3}\left( \omega_{4} \right)}} & \cdots \\ {B\quad{F_{5,1}\left( \omega_{5} \right)}} & {B\quad{F_{5,2}\left( \omega_{5} \right)}} & {B\quad{F_{5,3}\left( \omega_{5} \right)}} & \cdots \\ {\vdots\quad} & {\vdots\quad} & {\vdots\quad} & \quad \end{bmatrix} \cdot \begin{bmatrix} b_{1} \\ b_{2} \\ b_{3} \\ \vdots \end{bmatrix}} = \begin{bmatrix} {x\quad{F_{1}\left( \omega_{1} \right)}} \\ {{C_{1} \cdot x}\quad{F_{2}\left( \omega_{2} \right)}} \\ {{C_{2} \cdot x}\quad{F_{3}\left( \omega_{3} \right)}} \\ {\vdots\quad} \end{bmatrix}} & (14) \end{matrix}$

This equation is then solved exactly as described above in the sense of Least Mean Squares.

Output Only LMS

As mentioned earlier, it is also possible to calculate the pre-distorter by extracting only the output signal. Now, let us assume that the non-linearity is limited so that only minor non-linearities occur in the output signal. Then we might instead replace the signal “x” in Equations (4)-(9) by a filtered version of the amplifier signal “y”. The filter may be coarse enough just to drop spurious emissions outside a given main frequency band. The difference to the original input signal is then the in-band distortion, which can often be accepted. Moreover, it turns out that minimising out-of-band distortion will also have effect at in-band frequencies. Following this outlined path, the approximate solution to Equation (15) would be as outlined in Equation (16). a=[B(y)^(H) ·B(y)]⁻¹ ·B(y)^(H) ·x  (15) ã=[B(y)^(H) ·B(y)]⁻¹ ·B(y)^(H) ·filt{y}  (16)

Where filt{y}≈x is a filtered version of the output signal y (see FIG. 3). We may assume that, if the distortion is small enough, a filtered version of the output signal may approximate the input signal. The only knowledge that is required of the input signal is the average power relation to the output signal, and to what extent the output-signal replica should be filtered. The latter issue may be satisfied by for example only requiring that the intermodulation products (or spurious frequency response) should be zero below some pre-defined threshold level. Even though this filtered version of the output signal does indeed contain in-band distortion components; it is assumed that this level is low enough not to introduce large errors. Normally, devices used to amplify signals are from the beginning relatively linear, whereby the above statement of low enough distortion is automatically satisfied.

If the non-linear device is frequency dependent, the pre-distorter function can be improved by adding a pre-set frequency equalizer at the device input.

Direct Suppression of Spurious Frequencies

It is also possible to just suppressing the spurious frequency components of the output spectrum by just considering those frequencies alone. That is, without directly equating any inversion equation, we may suppress the unwanted spectrum directly. Let us as an example use the Volterra series expansion of the inverter in plain polynomial form without memory effects, and just setting the spurious frequencies to zero: a ₀ ·FFT(y)+a ₁ ·FFT(y ³)+a ₂ ·FFT(y ⁵) . . . =0|_(spurious frequencies)  (17) a ₁ ·FFT(y ³)+a ₂ ·FFT(y ⁵) . . . =−a ₀ ·FFT(y)|_(spurious frequencies)  (18)

In Equation (18), we only use those rows in the general matrix, which correspond to those particular frequencies where we would like the spectrum to become zero (See parts A and C in FIG. 4). As seen, the right-hand-side of Equation (18) contains the apparently unknown coefficient a₀. However, as we know the amplification through the system we also know this coefficient. So clearly, we again have a linear system of equations that can be solved by the LMS algorithm. The obvious benefit of the latter method is that we no longer use a substitute for the in-band signal for the optimisation. This avoids the LMS method trying to actually keep the output signal in the wanted frequency region, but rather tries to restore the input signal even in this frequency band.

It is also noted that the wanted in-band spectrum is not used in the formulation. This suggests that we would actually have no control of the in-band vector error. However, as the unwanted frequency components in Regions A and C in FIG. 4 are suppressed, then with a high confidence also the in-band spurious frequency components will also be suppressed.

Also in this case, if the non-linear device is frequency dependent, the pre-distorter function can be improved by adding a pre-set frequency equalizer at the device input.

Merits of Invention

Among the merits of this invention disclosure is the fact that a linear method can be applied to an inherently non-linear problem. The Least Mean Squares solution is applied in a classical way to directly extract the coefficients of a linear combination of Basis functions. As an example, the coefficients of a Volterra series can be readily applied and solved by this method.

The second merit of this disclosure is that frequency weighting of the cost-function may be obtained as to pronounce certain frequency regions in favour of other bands. It is noted that the mathematical formulation is still a linear one, and no iterative search algorithm is used to find the optimum solution to the problem.

The third merit of the invention is that output-only optimisation may be used effectively by reproducing the input signal characteristics from only the output signal and some minor knowledge such as wanted frequency band and power amplification.

The fourth merit is that the suggested improvement of just suppressing the unwanted frequency components gives the ability to pre-distort a non-linear device with the result of an output signal without vector errors. That is, the latter improvement searches to purely minimise the unwanted frequency components.

REFERENCES

-   [1] V. John Mathews, Giovanni L. Sicuranza, “Polynomial Signal     Processing”, ISBN 0471-03414-2 

1. A method for optimisation of pre-distortion of a non-linear device, characterised by the steps of solving coefficients of a linear expansion expression for an output signal of the non-linear device; expressing an inverter output signal as a linear combination of Basis functions, which equates an input signal of the non-linear device, whereby a solution for the coefficients of the linear expansion expression directly gives a pre-distorter function being an inverse operator to the non-linear device.
 2. The method for optimisation according to claim 1, characterised by the further steps of using the output signal of said non-linear device only as approximation of a target input signal of the non-linear device; filtering out spurious frequency components, whereby parameters for filtering are frequency components of amplitudes below a pre-set threshold value and adjusting a target input signal level by measuring linear gain of the non-linear device.
 3. The method for optimisation according to claim 1, characterised by the further steps of using the non-linear device output signal only by suppressing a spurious frequency spectrum directly in the frequency domain, whereby a target input signal of the non-linear device is considered to have frequency components of zero magnitude outside wanted spectrum.
 4. The method for optimisation according to claim 3, characterised by the further steps of expanding the output signal by a series representation, applying a Fourier transformation to each column of a matrix equation representing the output signal as a function of time to convert time problems into frequency domain, assigning a coefficient to a linear part of the expansion to satisfy a gain requirement, formulating a Least Mean Squares approach or equivalent for remaining coefficients.
 5. The method for optimisation according to claim 4, characterised by the further step of using for the series representation a dynamic Volterra series expansion.
 6. A method to optimise an inverse operator of a non-linear amplifier, characterised by the step of minimising an output signal spectrum of the inverse operator within certain frequency bands only using the amplifier output signal.
 7. The method according to claim 6, characterised by the further step of utilisation of different weighting factors in different frequency bands. 